CMOS DYNAMIC ELECTRICAL
BEHAVIOR
Both the speed and the
power consumption of a CMOS device depend to a large extent on AC or dynamic
characteristics of the device and its load, that is, what happens when the
output changes between states. As part of the internal design of CMOS ASICs,
logic designers must carefully examine the effects of output loading and
redesign where the load is too high. Even in board-level design, the effects of
loading must be considered for clocks, buses, and other signals that have high
fanout or long interconnections.
Speed depends on two
characteristics, transition time and propagation delay.
TRANSITION
TIME
The amount of time that the
output of a logic circuit takes to change from one state to another is called
the transition time. Fig.31(a) shows how we might like outputs to change
state—in zero time. However, real outputs cannot change instantaneously,
because they need time to charge the stray capacitance of the wires and other
components that they drive. A more realistic view of a circuit’s output is
shown in (b). An output takes a certain time, called the rise time (tr),
to change from LOW to HIGH, and a possibly different time, called the fall time (tf),
to change from HIGH to LOW.
Even Fig.31(b) is not quite
accurate, because the rate of change of the output voltage does not change
instantaneously, either. Instead, the beginning and the end of a transition are
smooth, as shown in (c). To avoid difficulties in defining the endpoints, rise
and fall times are normally measured at the boundaries of the valid logic
levels as indicated in the figure. With the convention in (c), the rise and
fall times indicate how long an output voltage takes to pass through the
“undefined” region between LOW
and HIGH. The initial part of a transition is not
included in the rise- or fall-time number. Instead, the initial part of a
transition contributes to the “propagation delay” number.
The rise and fall times of
a CMOS output depends mainly on two factors, the “on” transistor resistance and
the load capacitance.
A large capacitance increases
transition times; since this is undesirable, it is very rare for a logic designer
to purposely connect a capacitor to a logic circuit’s output. However, stray
capacitance (a capacitive load
or an AC Load) is present in every circuit; it comes from at
least three sources:
1. Output circuits, including
a gate’s output transistors, internal wiring, and packaging, have some
capacitance associated with them, on the order of 2-10 picofarads (pF) in
typical logic families, including CMOS.
2. The wiring that connects an
output to other inputs has capacitance, about 1 pF per inch or more, depending
on the wiring technology.
3. Input circuits, including
transistors, internal wiring, and packaging, have capacitance, from 2 to 15 pF
per input in typical logic families.
A CMOS output’s rise and
fall times can be analyzed using the equivalent circuit shown in Fig.32. The p-channel
and n-channel transistors are modeled by resistances Rp and Rn,
respectively. In normal operation, one resistance is high and the other is low,
depending on the output’s state.
The output’s load is
modeled by an equivalent load circuit with three components:
RL, VL These two components
represent the DC load and determine the voltages and currents that are present
when the output has settled into a stable HIGH or LOW state. The DC load doesn’t
have too much effect on transition times when the output changes states.
CL This capacitance represents
the AC load and determines the voltages and currents that are present while the
output is changing, and how long it takes to change from one state to the other.
When a CMOS output drives only CMOS inputs, the DC load is negligible. To simplify
matters, we’ll analyze only this case, with RL = ∞ and VL =
0, in the remainder of this
subsection. The presence of a non-negligible DC load would affect the results,
but not dramatically.
For the purposes of this
analysis of the transition times of a CMOS output, Assume CL= 100 pF, a moderate capacitive load and the “on”
resistances of the p-channel and n-channel transistors are 200Ω and
100Ω, respectively.
The rise and fall times
depend on how long it takes to charge or discharge the capacitive load CL.
The electrical conditions in the
circuit when the output is in a steady HIGH state as shown in Fig.33(a). (RL
and VL are not drawn; they have no effect, since we assume RL
= ∞.)
Assume that when CMOS transistors change between “on” and “off,” they do so
instantaneously. Assume at time t = 0 the CMOS output changes to the LOW state,
resulting in the situation as shown in (b).
At time t = 0,
VOUT is still 5.0 V. (A useful electrical engineering maxim
is that the voltage across a capacitor cannot change instantaneously.) At time t
= ∞,
the capacitor must be fully discharged and VOUT will be 0 V.
In between, the value of VOUT is governed by an exponential
law:
The factor RnCL
has units of seconds, and is called an RC time constant. The preceding
calculation shows that the RC time constant for HIGH-to-LOW transitions is 10 nanoseconds (ns).
Fig.34 shows VOUT as a function
of time. To calculate fall time, consider 1.5 V and 3.5 V are the defined
boundaries for LOW and HIGH levels for CMOS inputs being driven by
the CMOS output. To obtain the fall time, solve the preceding equation for VOUT
= 3.5 and VOUT =1.5, yielding:
The fall time tf is
the difference between these two numbers, or about 8.5 ns.
For calculation of Rise time, consider Fig.35(a)
that shows the conditions in the circuit when the output is in a steady LOW state.
If at time t = 0 the CMOS output changes to the HIGH state,
the situation depicted in (b) results. Once again, VOUT
cannot change instantly, but at time t = ∞, the capacitor will be fully charged
and VOUT will be 5V.
The value of VOUT in
between is governed by an exponential law:
The RC time constant in this
case is 20 ns. Fig.36 plots VOUT as a function of time. To
obtain the rise time, solve the preceding equation for VOUT = 1.5
and VOUT = 3.5, yielding
The rise time tr is the
difference between these two numbers, or about 17 ns. Assume the p-channel
transistor has twice the resistance of the n-channel one, and as a
result the rise time is twice as long as the fall time. It takes longer for the
“weak” p-channel transistor to pull the output up than it does for the
“strong” n-channel transistor to pull it down; the output’s drive
capability is “asymmetric.” High-speed CMOS devices are sometimes fabricated
with larger p-channel transistors to make the transition times more nearly
equal and output drive more symmetric.
Regardless of the transistors’
characteristics, an increase in the load capacitance cause an increase in the RC
time constant, and a corresponding increase in the transition times of the
output. Thus, it is a goal of high-speed circuit designers to minimize load
capacitance, especially on the most timing-critical signals, i.e., by
minimizing the number of inputs driven by the signal, by creating multiple
copies of the signal, and by careful physical layout of the circuit.
Practically for digital circuits, the transition times are
estimated, without going through a detailed analysis. A useful rule of thumb is
that the transition time approximately equals the RC time constant of
the charging or discharging circuit.
Manufacturers of commercial CMOS circuits typically do not specify
transistor “on” resistances on their data sheets, but the same information
published in the manufacturers’ application notes.
An “on” resistance can be estimated as the voltage drop across the
“on” transistor divided by the current through it with a worst-case resistive
load by using
Rise and fall times only
partially describe the dynamic behavior of a logic element; we need additional
parameters to relate output timing to input timing.
A signal path is the
electrical path from a particular input signal to a particular output signal of
a logic element.
The propagation delay tp
of a signal path is the amount of time that it takes for a change in the input
signal to produce a change in the output signal.
A complex logic element
with multiple inputs and outputs may specify a different value of tp for
each different signal path. Also, different values may be specified for a
particular signal path, depending on the direction of the output change.
Ignoring rise and fall
times, Fig.37(a) shows two different propagation delays for the input-to-output
signal path of a CMOS inverter, depending on the direction of the output
change:
tpHL - The time between an input change and the corresponding
output change when the output is changing from HIGH to LOW.
tpLH - The time between an input change and the corresponding
output change when the output is changing from LOW to HIGH.
There are several factors which
lead to nonzero propagation delays like
·
In a CMOS device, the rate at which transistors change state is influenced
both by the semiconductor physics of the device and by the circuit environment,
including input-signal transition rate, input capacitance, and output loading.
·
Multistage devices such as noninverting gates or more complex
logic functions may require several internal transistors to change state before
the output can change state.
·
Even when the output begins to change state, with nonzero rise and
fall times it takes quite some time to cross the region between states.
All of these factors are included
in propagation delay.
To factor out the effect of
rise and fall times, manufacturers usually specify
propagation delays at the
midpoints of input and output transitions, as shown in Fig.37(b). However,
sometimes the delays are specified at the logic-level boundary points,
especially if the device’s operation may be adversely affected by slow rise and
fall times.
Eg., Fig.38 shows how the
minimum input pulse width for an SR
latch might be specified. In addition, a manufacturer may specify
absolute maximum input rise and fall times that must be satisfied to guarantee
proper operation. High-speed CMOS circuits may consume excessive current or
oscillate if their input transitions are too slow.
Power
Consumption
The power consumption of a
CMOS circuit whose output is not changing is
called static power
dissipation or quiescent power dissipation. Most CMOS circuits have
very low static power dissipation, hence they are attractive for laptop
computers and other low-power applications—when computation pauses, very little
power is consumed. A CMOS circuit consumes significant power only during transitions;
this is called dynamic power dissipation.
One source of dynamic power
dissipation is the partial short-circuiting of the CMOS output structure. When
the input voltage is not close to one of the power supply rails (0V or VCC),
both the p-channel and n-channel output transistors may be
partially “on,” creating a series resistance of 600Ω or less. In this case, current flows through the
transistors from VCC to ground. The amount of power consumed
in this way depends on both the value of VCC and the rate at which
output transitions occur, according to the formula
Where
PT - The circuit’s internal power dissipation due to output
transitions.
VCC - The power supply voltage. As all electrical engineers know, power
dissipation across a resistive load (the partially-on transistors) is proportional
to the square of the voltage.
f - The transition frequency of the
output signal, specifies the number of power-consuming output transitions per
second. (frequency is defined as the number of transitions divided by 2.)
CPD - The power dissipation capacitance is a constant, normally specified by
the device manufacturer, completes the formula. CPD turns out to have
units of capacitance, but does not represent an actual output capacitance.
Rather, it embodies the
dynamics of current flow through the changing output-transistor resistances
during a single pair of output transitions, HIGH-to-LOW and LOW-to-HIGH.
Eg., CPD
for HC-series CMOS gates is typically 20–24 pF, even though the actual output
capacitance is much less.
The PT
formula is valid only if input transitions are fast enough, leading to fast
output transitions. If the input transitions are too slow, then the output transistors stay partially on for a
longer time, and power consumption increases. Device
manufacturers usually recommend a maximum input rise and fall time, below which
the value specified for CPD is valid.
Another more significant source of CMOS
power consumption is the capacitive load (CL) on the output.
During a LOW-to-HIGH transition,
current flows through a p-channel transistor to charge CL.
Likewise, during a HIGH-to-LOW transition, current flows through an n-channel
transistor to discharge CL. In each case, power is dissipated
in the “on” resistance of the transistor. The PL is used to
denote the total amount of power dissipated by charging and discharging CL.
The units of PL are power, or energy usage per unit time. The energy for
one transition could be determined by calculating the current through the
charging transistor as a function of time, squaring this function, multiplying
by the “on” resistance of the charging transistor, and integrating over time.
During a transition, the voltage across
the load capacitance CL changes by ±VCC.
According to the definition of capacitance, the total amount of charge that must
flow to make a voltage change of VCC across CL
is CL
* VCC. The total amount of
energy used in one transition is charge times the average voltage change. The
first little bit of charge makes a voltage change of VCC,
while the last bit of charge makes a vanishingly small voltage change, hence
the average change is VCC/2. The total energy per transition
is therefore CL*VCC2/2.
If there are 2f transitions per second, the total power dissipated due
to the capacitive load is
The total dynamic power dissipation of
a CMOS circuit is the sum of PT and PL:
Based on this formula, dynamic power
dissipation is often called CV2f power. In most
applications of CMOS circuits, CV2f power is the major
contributor to total power dissipation. CV2f power is
also consumed by bipolar logic circuits like TTL and ECL, but at low to
moderate frequencies it is insignificant compared to the static (DC or
quiescent) power dissipation of bipolar circuits.
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